|Category||Analog & Mixed-Signal Processing => Amplifiers => Current Feedback|
|Description||Radiation Hardened, High Speed, Low Power Current Feedback Amplifier With Programmable Output Limiting|
|Datasheet||Download 5962F9676701VPC datasheet
|Cross ref.||Similar parts: LMH6702QML-SP|
Radiation Hardened, High Speed, Low Power Current Feedback Amplifier with Programmable Output Limiting
The is a radiation hardened, high speed, low power current feedback amplifier built with Intersil's proprietary complementary bipolar UHF-1 (DI bonded wafer) process. They are QML approved and processed in full compliance with MIL-PRF-38535. This amplifier features user programmable output limiting, via the VH and VL pins. The HS-1135RH is the ideal choice for high speed, low power applications requiring output limiting (e.g., flash A/D drivers), especially those requiring fast overdrive recovery times. The limiting function allows the designer to set the maximum and minimum output levels to protect downstream stages from damage or input saturation. The subnanosecond overdrive recovery time ensures a quick return to linear operation following an overdrive condition. Component and composite video systems also benefit from this op amp's performance, as indicated by the gain flatness, and differential gain and phase specifications. Specifications for Rad Hard QML devices are controlled by the Defense Supply Center in Columbus (DSCC). The SMD numbers listed here must be used when ordering. Detailed Electrical Specifications for these devices are contained in SMD 5962-96767. A "hot-link" is provided on our homepage for downloading. http://www.intersil.com/spacedefense/space.htmFeatures
Electrically Screened to SMD # 5962-96767 QML Qualified per MIL-PRF-38535 Requirements User Programmable Output Voltage Limiting Fast Overdrive Recovery. <1ns (Typ) Low Supply Current. 6.9mA (Typ) Wide -3dB Bandwidth.360MHz (Typ) High Slew Rate.1200V/µs (Typ) High Input Impedance. 2M (Typ) Excellent Gain Flatness (to 50MHz). ±0.07dB (Typ) Total Gamma Dose. 300kRAD(Si) Latch Up. None (DI Technology)Applications
Flash A/D Driver Video Switching and Routing Pulse and Video Amplifiers Wideband Amplifiers RF/IF Signal Processing Imaging Systems
ORDERING NUMBER 5962F9676701VPC HS7-1135RH/PROTO INTERNAL MKT. NUMBER HS7B-1135RH-Q HS7-1135RH/PROTO TEMP. RANGE (oC) to 125
CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures. 321-724-7143 | Copyright © Intersil Corporation 1999
The HS-1135RH features user programmable output clamps to limit output voltage excursions. Clamping action is obtained by applying voltages to the VH and VL terminals (pins 8 and 5) of the amplifier. VH sets the upper output limit, while VL sets the lower clamp level. If the amplifier tries to drive the output above VH, or below VL, the clamp circuitry limits the output voltage VL ( the clamp accur acy), respectively. The low input bias currents of the clamp pins allow them to be driven by simple resistive divider circuits, or active elements such as amplifiers or DACs. the clamp inputs floating. A similar description applies to the symmetrical low clamp circuitry controlled by VL. When the output is clamped, the negative input continues to source a slewing current (ICLAMP) in an attempt to force the output to the quiescent voltage defined by the input. QP5 must sink this current while clamping, because the -IN current is always mirrored onto the high impedance node. The clamping current is calculated as (V-IN - VOUT)/RF. As an example, a unity gain circuit with VIN = 1V, and = 510 would have ICLAMP = 1.96mA. Note that ICC will increase by ICLAMP when the output is clamp limited.
The clamped output voltage will not be exactly equal to the voltage applied VH or VL. Offset errors, mostly due to VBE mismatches, necessitate a clamp accuracy parameter which is found in the device specifications. Clamp accuracy is a function of the clamping conditions. Referring again to Figure 1, it can be seen that one component of clamp accuracy is the VBE mismatch between the QX6 transistors, and the QX5 transistors. If the transistors always ran at the same current level there would be no VBE mismatch, and no contribution to the inaccuracy. The QX6 transistors are biased at a constant current, but as described earlier, the current through QX5 is equivalent to ICLAMP. VBE increases as ICLAMP increases, causing the clamped output voltage to increase as well. ICLAMP is a function of the overdrive level (V-IN -VOUTCLAMPED) and RF, so clamp accuracy degrades as the overdrive increases, as RF decreases. As an example, the specified accuracy of ±60mV for a 2X overdrive with = 510 degrades to ±220mV for 240 at the same overdrive, to ±250mV for a 3X overdrive with = 510. Consideration must also be given to the fact that the clamp voltages have an effect on amplifier linearity. The "Nonlinearity Near Clamp Voltage" curve in the data sheet illustrates the impact of several clamp levels on linearity.
Figure 1 shows a simplified schematic of the HS-1135RH input stage, and the high clamp (VH) circuitry. As with all current feedback amplifiers, there is a unity gain buffer - QX2) between the positive and negative inputs. This buffer forces -IN to track +IN, and sets up a slewing current of (VIN - VOUT)/RF. This current is mirrored onto the high impedance node (Z) by QX3-QX4, where it is converted to a voltage and fed to the output via another unity gain buffer. If no clamping is utilized, the high impedance node may swing within the limits defined by QP4 and QN4. Note that when the output reaches it's quiescent value, the current flowing through -IN is reduced to only that small current (-IBIAS) required to keep the output at the final voltage.
Unlike some competitor devices, both VH and VL have usable ranges that cross 0V. While VH must be more positive than VL, both may be positive or negative, within the range restrictions indicated in the specifications. For example, the HS-1135RH could be limited to ECL output levels by setting = -0.8V and -1.8V. VH and VL may be connected to the same voltage (GND for instance) but the result won't a DC output voltage from an AC input signal. 200mV AC signal will still be present at the output.
Tracing the path from to Z illustrates the effect of the clamp voltage on the high impedance node. VH decreases 2VBE (QN6 and QP6) to set up the base voltage QP5. QP5 begins to conduct whenever the high impedance node reaches a voltage equal to QP5's base 2VBE (QP5 and QN5). Thus, QP5 clamps node Z whenever Z reaches VH. R1 provides a pull-up network to ensure functionality with
The output voltage remains at the clamp level as long as the overdrive condition remains. When the input voltage drops below the overdrive level (VCLAMP /AVCL) the amplifier will return to linear operation. A time delay, known as the Overdrive Recovery Time, is required for this resumption of linear operation. The plots of "Unclamped Performance" and "Clamped Performance" highlight the HS-1135RH's
subnanosecond recovery time. The difference between the unclamped and clamped propagation delays is the overdrive recovery time. The appropriate propagation delays are 4.0ns for the unclamped pulse, and 4.8ns for the clamped (2X overdrive) pulse yielding an overdrive recovery time of 800ps. The measurement uses the 90% point of the output transition to ensure that linear operation has resumed. Note: The propagation delay illustrated is dominated by the fixturing. The delta shown is accurate, but the true HS-1135RH propagation delay is 500ps. The layout and schematic of the board are shown here:
This amplifier is designed with compensation to negate the package parasitics that typically lead to instabilities. As a result, the use of die in hybrid applications results in overcompensated performance due to lower parasitic capacitances. Reducing RF below the recommended values for packaged units will solve the problem. For = +2 the recommended starting point is 300, while unity gain applications should try 400.
The frequency performance of this amplifier depends a great deal on the amount of care taken in designing the PC board. The use of low inductance components such as chip resistors and chip capacitors is strongly recommended, while a solid ground plane is a must! Attention should be given to decoupling the power supplies. A large value (10µF) tantalum in parallel with a small value chip (0.1µF) capacitor works well in most cases. Terminated microstrip signal lines are recommended at the input and output of the device. Output capacitance, such as that resulting from an improperly terminated transmission line will degrade the frequency response of the amplifier and may cause oscillations. In most cases, the oscillation can be avoided by placing a resistor in series with the output. Care must also be taken to minimize the capacitance to ground seen by the amplifier's inverting input. The larger this capacitance, the worse the gain peaking, resulting in pulse overshoot and possible instability. To this end, it is recommended that the ground plane be removed under traces connected to pin 2, and connections to pin 2 should be kept as short as possible. An example of a good high frequency layout is the Evaluation Board shown in Figure 2.FIGURE 2C. SCHEMATIC FIGURE 2. EVALUATION BOARD SCHEMATIC AND LAYOUT
An evaluation board is available for the HS-1135RH, (HFA11XXEVAL). Please contact your local sales office for information.
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