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Part: 8001401Z
Category:
Analog & Mixed-Signal Processing
-> Amplifiers
-> Operational Amplifiers
Description: Operational Amplifier, Replacement For LH0033/EL2005
Company: M.S. Kennedy
Datasheet: Download 8001401Z datasheet File size : 344 kB
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Datasheet text preview:
ISO 9001 CERTIFIED BY DSCC
M.S.KENNEDY CORP. FEATURES:
FET INPUT HIGH SPEED VOLTAGE FOLLOWER/BUFFER AMPLIFIER
0033
(315) 701-6751
4707 Dey Road Liverpool, N.Y. 13088 Industry Wide LH0033/EL2005 Replacement Low Input Offset - 2mV Low Input Offset Drift - 25µV/°C FET Input, Low Input Current - 50pA High Slew Rate - 1500V/µS Wide Bandwidth - 140MHz High Output Current - ±100mA Available to DSCC SMD 5962-80014
MIL-PRF-38534 CERTIFIED
DESCRIPTION:
The MSK 0033(B) is a high speed, wide bandwidth voltage follower/buffer amplifier that is pin compatible with all other 0033 designs. The FET input is cascaded to force the input characteristics to remain constant over the full input voltage range. Significantly improved performance in sample and hold circuits is achieved since the DC bias current remains constant with input voltage. The FET input also makes the MSK 0033 very accurate since it produces extremely low input bias current, input offset voltage and input offset voltage drift specifications. Transistion times in the range of 2.5 nS make the MSK 0033 fast enough for most high speed voltage follower/buffer amplifier applications.
EQUIVALENT SCHEMATIC
TYPICAL APPLICATIONS
Sample And Hold Impedance Buffers For A to D's High Speed Line Drivers CRT Deflection Driver 1 2 3 4 5 6
PIN-OUT INFORMATION
Positive Driver Power Supply N/C N/C N/C Input Offset Preset 1 7 8 9 10 11 12 Offset Adjust N/C Negative Driver Power Supply Negative Power Supply Output Positive Power Supply Rev. B 7/00
ABSOLUTE MAXIMUM RATINGS
ELECTRICAL SPECIFICATIONS
Parameter STATIC Supply Voltage Range Quiescent Current INPUT Offset Voltage Offset Voltage Drift Offset Adjust Input Bias Current 9 Input Impedance 3 Power Supply Rejection Ratio 2 Input Noise Density 3 Input Noise Voltage 3 OUTPUT Output Voltage Swing Output Current Settling Time to 1% 2 3 Bandwidth (-3dB) 3 TRANSFER CHARACTERISTICS Slew Rate Voltage Gain VOUT=±10V RS=100 VIN=1VRMS F=1KHz 4 4 1000 0.97 1500 0.99 1000 0.95 1500 0.98 V/µS V/V VIN=±14V RL=1K VIN=±10.5V RL=100 2V step VIN=1VRMS RL=1K 4 4 ±12 ±90 ±12.5 ±110 25 140 ±12 ±90 ±12.5 ±110 25 140 V mA nS MHz Short Pin 6 to Pin 7 VIN=0V Short Pin 6 to Pin 7 VIN=0V Pin 6=open RPOT=200 From Pin 7 to Pin 9 VCM=0V Either Input F=DC ±10VVS±20V F=10Hz to 1KHz F=1KHz 1 2,3 1,2,3 1 2,3 65 ±2.0 ±25 ±50 ±2 10 75 1.5 40
12
Test Conditions
Group A Subgroup -
MSK 0033B Min. ±10 Typ. ±15 ±19 Max. ±18 ±22 ±10 ±250 ±100 ±10 Min. ±10 60 -
MSK 0033 Typ. ±15 ±19 ±5 Adjust to Zero ±50 ±2 10 75 1.5 40
12
Max. ±18 ±25 ±15 ±500 -
38
VIN=0V
1
Adjust to Zero
NOTES:
Unless otherwise specified ±VCC = ±15 VDC. Measured within a high speed amplifier feedback loop. Devices shall be capable of meeting the parameter, but need not be tested. Typical parameters are for reference only. Industrial grade devices shall be tested to subgroups 1 and 4 unless otherwise specified. Military grade devices ('B' suffix) shall be 100% tested to subgroups 1,2,3 and 4. Subgroup 5 and 6 testing available upon request. Subgroup 1,4 TA=TC=+25°C Subgroup 2,5 TA=TC=+125°C Subgroup 3,6 TA=TC=-55°C 8 Electrical specifications are derated for power supply voltages other than ±15VDC. 9 Measurement made 0.5 seconds after application of power. Actual DC continuous test limit is 2.5 nA at 25°C 1 2 3 4 5 6 7
2
Rev. B 7/00
TJ RTH
±VCC IOUT VIN TC
Supply Voltage ±20V Output Current ±120mA Differential Input Voltage ±20V Case Operating Temperature (MSK 0033B) -55°C to +125°C (MSK 0033) -40°C to +85°C
TST TLD
Storage Temperature Range -65°C to +150°C Lead Temperature Range 300°C (10 Seconds) Junction Temperature 175°C Thermal Resistance 65°C/W Junction to Case Output Devices Only
Units V mA mV µV/°C mV pA nA dB µVRMS nV/Hz
APPLICATION NOTES HEAT SINKING
To determine if a heat sink is necessary for your application and if so, what type, refer to the thermal model and governing equation below. RSA = ((TJ - TA)/PD) - (RJC) - (RCS) = ((125°C - 80°C) / .64W) - 65°C/W - .15°C/W = 70.3 - 65.15 = 5.2°C/W The heat sink in this example must have a thermal resistance of no more than 5.2°C/W to maintain a junction temperature of no more than +125°C.
Thermal Model:
OFFSET VOLTAGE ADJUST
See Figure 1. To externally null the offset voltage, connect a 200 potentiometer between Pins 7 and 10 and leave Pin 6 open. If offset null is not necessary, short Pin 6 to Pin 7 and remove the 200 potentiometer. Do not connect Pin 7 to Vcc.
Governing Equation:
TJ=PD x (RJC + RCS + RSA) + TA Where TJ = Junction Temperature PD = Total Power Dissipation RJC = Junction to Case Thermal Resistance RCS = Case to Heat Sink Thermal Resistance RSA = Heat Sink to Ambient Thermal Resistance TC = Case Temperature TA = Ambient Temperature TS = Sink Temperature
Example:
This example demonstrates a worst case analysis for the buffer output stage. This occurs when the output voltage is 1/2 the power supply voltage. Under this condition, maximum power transfer occurs and the output is under maximum stress. Conditions: VCC = ±16VDC VO = ±8Vp Sine Wave, Freq. = 1KHz RL = 100 For a worst case analysis we will treat the ±8Vp sine wave as an 8 VDC output voltage. 1.) Find Driver Power Dissipation PD = (VCC-VO) (VO/RL) = (16V-8V) (8V/100) = 640mW 2.) For conservative design, set TJ=+125°C Max. 3.) For this example, worst case TA=+80°C 4.) RJC = 65°C/W from MSK 0033B Data Sheet 5.) RCS = 0.15°C/W for most thermal greases 6.) Rearrange governing equation to solve for RSA
CURRENT LIMITING
See Figure 1. If no current limit is required, short Pin 1 to Pin 12 and Pin 9 to Pin 10 and delete Q1 thru Q4 connections. Q1 through Q4 and the Rlim resistors form a current source current limit scheme and current limit resistor values can be calculated as follows: +Rlim Vbe -Rlim Vbe Isc Isc Since current limit is directly proportional to the base-emitter voltage drop of the 2N2222's and 2N2907's in the current limit scheme, the current limit value will change slightly with ambient temperature changes. The base-emitter voltage drop will decrease as temperature increases causing the actual current limit point to decrease.
POWER SUPPLY BYPASSING
Both the negative and the positive power supplies must be effectively decoupled with a high and low frequency bypass circuit to avoid power supply induced oscillation. An effective decoupling scheme consists of a 0.1 microfarad ceramic capacitor in parallel with a 4.7 microfarad tantalum capacitor from each power supply pin to ground.
3
Rev. B 7/00
TYPICAL APPLICATIONS
4
Rev. B 7/00
TYPICAL PERFORMANCE CURVES
5
Rev. B 7/00
Others parts begin by 80
80-1 80-2 80-3
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